This article illustrates some typical **operational amplifier applications**. A non-ideal operational amplifier's equivalent circuit has a finite input impedance, a non-zero output impedance, and a finite gain. A real op-amp has a number of non-ideal features as shown in the diagram, but here a simplified schematic notation is used, many details such as device selection and power supply connections are not shown. Operational amplifiers are optimised for use with negative feedback, and this article discusses only negative-feedback applications. When positive feedback is required, a comparator is usually more appropriate. See Comparator applications for further information.

In order for a particular device to be used in an application, it must satisfy certain requirements. The operational amplifier must

- have large open-loop signal gain (voltage gain of 200,000 is obtained in early integrated circuit exemplars), and
- have input impedance large with respect to values present in the feedback network.

With these requirements satisfied, the op-amp is considered ideal, and one can use the method of virtual ground to quickly and intuitively grasp the 'behavior' of any of the op-amp circuits below.

Resistors used in practical solid-state op-amp circuits are typically in the kΩ range. Resistors much greater than 1 MΩ cause excessive thermal noise and make the circuit operation susceptible to significant errors due to bias or leakage currents.

Practical operational amplifiers draw a small current from each of their inputs due to bias requirements (in the case of bipolar junction transistor-based inputs) or leakage (in the case of MOSFET-based inputs).

These currents flow through the resistances connected to the inputs and produce small voltage drops across those resistances. Appropriate design of the feedback network can alleviate problems associated with input bias currents and common-mode gain, as explained below. The heuristic rule is to ensure that the impedance "looking out" of each input terminal is identical.

To the extent that the input bias currents do not match, there will be an effective input offset voltage present, which can lead to problems in circuit performance. Many commercial op-amp offerings provide a method for tuning the operational amplifier to balance the inputs (e.g., "offset null" or "balance" pins that can interact with an external voltage source attached to a potentiometer). Alternatively, a tunable external voltage can be added to one of the inputs in order to balance out the offset effect. In cases where a design calls for one input to be short-circuited to ground, that short circuit can be replaced with a variable resistance that can be tuned to mitigate the offset problem.

Operational amplifiers using MOSFET-based input stages have input leakage currents that will be, in many designs, negligible.

Although power supplies are not indicated in the (simplified) operational amplifier designs below, they are nonetheless present and can be critical in operational amplifier circuit design.

Power supply imperfections (e.g., power signal ripple, non-zero source impedance) may lead to noticeable deviations from ideal operational amplifier behavior. For example, operational amplifiers have a specified power supply rejection ratio that indicates how well the output can reject signals that appear on the power supply inputs. Power supply inputs are often noisy in large designs because the power supply is used by nearly every component in the design, and inductance effects prevent current from being instantaneously delivered to every component at once. As a consequence, when a component requires large injections of current (e.g., a digital component that is frequently switching from one state to another), nearby components can experience sagging at their connection to the power supply. This problem can be mitigated with appropriate use of bypass capacitors connected across each power supply pin and ground. When bursts of current are required by a component, the component can *bypass* the power supply by receiving the current directly from the nearby capacitor (which is then slowly recharged by the power supply).

Additionally, current drawn into the operational amplifier from the power supply can be used as inputs to external circuitry that augment the capabilities of the operational amplifier. For example, an operational amplifier may not be fit for a particular high-gain application because its output would be required to generate signals outside of the safe range generated by the amplifier. In this case, an external push–pull amplifier can be controlled by the current into and out of the operational amplifier. Thus, the operational amplifier may itself operate within its factory specified bounds while still allowing the negative feedback path to include a large output signal well outside of those bounds.

The first example is the differential amplifier, from which many of the other applications can be derived, including the inverting, non-inverting, and summing amplifier, the voltage follower, integrator, differentiator, and gyrator.

Main article: Differential amplifier |

Amplifies the difference in voltage between its inputs.

- The name "differential amplifier" must not be confused with the "differentiator", which is also shown on this page.

- The "instrumentation amplifier", which is also shown on this page, is a modification of the differential amplifier that also provides high input impedance.

The circuit shown computes the difference of two voltages, multiplied by some gain factor. The output voltage

Or, expressed as a function of the common-mode input *V*_{com} and difference input *V*_{dif}:

the output voltage is

In order for this circuit to produce a signal proportional to the voltage difference of the input terminals, the coefficient of the *V*_{com} term (the common-mode gain) must be zero, or

With this constraint^{[nb 1]} in place, the common-mode rejection ratio of this circuit is infinitely large, and the output

where the simple expression *R*_{f} / *R*_{1} represents the closed-loop gain of the differential amplifier.

The special case when the closed-loop gain is unity is a differential follower, with

An inverting amplifier is a special case of the differential amplifier in which that circuit's non-inverting input *V*_{2} is grounded, and inverting input *V*_{1} is identified with *V*_{in} above. The closed-loop gain is *R*_{f} / *R*_{in}, hence

- .

The simplified circuit above is like the differential amplifier in the limit of *R*_{2} and *R*_{g} very small. In this case, though, the circuit will be susceptible to input bias current drift because of the mismatch between *R*_{f} and *R*_{in}.

To intuitively see the gain equation above, calculate the current in *R*_{in}:

then recall that this same current must be passing through *R*_{f}, therefore (because *V*_{−} = *V*_{+} = 0):

A mechanical analogy is a seesaw, with the *V*_{−} node (between *R*_{in} and *R*_{f}) as the fulcrum, at ground potential. *V*_{in} is at a length *R*_{in} from the fulcrum; *V*_{out} is at a length *R*_{f}. When *V*_{in} descends "below ground", the output *V*_{out} rises proportionately to balance the seesaw, and *vice versa*.^{[1]}

As the negative input of the op-amp acts as a virtual ground, the input impedance of this circuit is equal to *R*_{in}.

A non-inverting amplifier is a special case of the differential amplifier in which that circuit's inverting input *V*_{1} is grounded, and non-inverting input *V*_{2} is identified with *V*_{in} above, with *R*_{1} ≫ *R*_{2}.
Referring to the circuit immediately above,

- .

To intuitively see this gain equation, use the virtual ground technique to calculate the current in resistor *R*_{1}:

then recall that this same current must be passing through *R*_{2}, therefore:

Unlike the inverting amplifier, a non-inverting amplifier cannot have a gain of less than 1.

A mechanical analogy is a class-2 lever, with one terminal of *R*_{1} as the fulcrum, at ground potential. *V*_{in} is at a length *R*_{1} from the fulcrum; *V*_{out} is at a length *R*_{2} further along. When *V*_{in} ascends "above ground", the output *V*_{out} rises proportionately with the lever.

The input impedance of the simplified non-inverting amplifier is high:

where *Z*_{dif} is the op-amp's input impedance to differential signals, and *A*_{OL} is the open-loop voltage gain of the op-amp (which varies with frequency), and *B* is the feedback factor (the fraction of the output signal that returns to the input).^{[2]}^{[3]} In the case of the ideal op-amp, with *A*_{OL} infinite and *Z*_{dif} infinite, the input impedance is also infinite. In this case, though, the circuit will be susceptible to input bias current drift because of the mismatch between the impedances driving the *V*_{+} and *V*_{−} op-amp inputs.

The feedback loop similarly decreases the output impedance:

where *Z*_{out} is the output impedance with feedback, and *Z*_{OL} is the open-loop output impedance.^{[3]}

Used as a buffer amplifier to eliminate loading effects (e.g., connecting a device with a high source impedance to a device with a low input impedance).

- (realistically, the differential input impedance of the op-amp itself (1 MΩ to 1 TΩ), multiplied by the open-loop gain of the op-amp)

Due to the strong (i.e., unity gain) feedback and certain non-ideal characteristics of real operational amplifiers, this feedback system is prone to have poor stability margins. Consequently, the system may be unstable when connected to sufficiently capacitive loads. In these cases, a lag compensation network (e.g., connecting the load to the voltage follower through a resistor) can be used to restore stability. The manufacturer data sheet for the operational amplifier may provide guidance for the selection of components in external compensation networks. Alternatively, another operational amplifier can be chosen that has more appropriate internal compensation.

The input and output impedance are affected by the feedback loop in the same way as the non-inverting amplifier, with *B*=1.^{[2]}^{[3]}

A summing amplifier sums several (weighted) voltages:

- When , and independent

- When

- Output is inverted
- Input impedance of the
input is ( is a virtual ground)*n*th

Main article: Instrumentation amplifier |

Combines very high input impedance, high common-mode rejection, low DC offset, and other properties used in making very accurate, low-noise measurements

- Is made by adding a non-inverting buffer to each input of the differential amplifier to increase the input impedance.

Main article: Wien bridge oscillator |

Produces a very low distortion sine wave. Uses negative temperature compensation in the form of a light bulb or diode.

Main article: Active filter |

Operational amplifiers can be used in construction of active filters, providing high-pass, low-pass, band-pass, reject and delay functions. The high input impedance and gain of an op-amp allow straightforward calculation of element values, allowing accurate implementation of any desired filter topology with little concern for the loading effects of stages in the filter or of subsequent stages. However, the frequencies at which active filters can be implemented is limited; when the behavior of the amplifiers departs significantly from the ideal behavior assumed in elementary design of the filters, filter performance is degraded.

Main article: Comparator |

Main article: Comparator applications |

An operational amplifier can, if necessary, be forced to act as a comparator. The smallest difference between the input voltages will be amplified enormously, causing the output to swing to nearly the supply voltage. However, it is usually better to use a dedicated comparator for this purpose, as its output has a higher slew rate and can reach either power supply rail. Some op-amps have clamping diodes on the input that prevent use as a comparator.^{[4]}

Main article: Op amp integrator |

The integrator is mostly used in analog computers, analog-to-digital converters and wave-shaping circuits.

Integrates (and inverts) the input signal *V*_{in}(*t*) over a time interval *t*, *t*_{0} < *t* < *t*_{1}, yielding an output voltage at time *t* = *t*_{1} of

where *V*_{out}(*t*_{0}) represents the output voltage of the circuit at time *t* = *t*_{0}. This is the same as saying that the output voltage changes over time *t*_{0} < *t* < *t*_{1} by an amount proportional to the time integral of the input voltage:

This circuit can be viewed as a low-pass electronic filter, one with a single pole at DC (i.e., where ) and with gain.

In a practical application one encounters a significant difficulty:
unless the capacitor *C* is periodically discharged, the output voltage will eventually drift outside of the operational amplifier's operating range.
This can be due to any combination of:

- The input
*V*_{in}has a non-zero DC component, - Input bias current is non-zero,
- Input offset voltage is non-zero.
^{[5]}

A slightly more complex circuit can ameliorate the second two problems, and in some cases, the first as well.

Here, the feedback resistor R_{f} provides a discharge path for capacitor C_{f}, while the series resistor at the non-inverting input R_{n}, when of the correct value, alleviates input bias current and common-mode problems. That value is the parallel resistance of R_{i} and R_{f}, or using the shorthand notation ||:

The relationship between input signal and output signal is now

Main article: Differentiator § Active differentiator |

Differentiates the (inverted) signal over time:

where and are functions of time.

The transfer function of the inverting differentiator has a single zero in the origin (i.e., where angular frequency ). The high-pass characteristics of a differentiating amplifier can lead to stability challenges when the circuit is used in an analog servo loop (e.g., in a PID controller with a significant derivative gain). In particular, as a root locus analysis would show, increasing feedback gain will drive a closed-loop pole toward marginal stability at the DC zero introduced by the differentiator.

Main article: Gyrator |

Simulates an inductor (i.e., provides inductance without the use of a possibly costly inductor). The circuit exploits the fact that the current flowing through a capacitor behaves through time as the voltage across an inductor. The capacitor used in this circuit is geometrically smaller than the inductor it simulates, and its capacitance is less subject to changes in value due to environmental changes. Applications where this circuit may be superior to a physical inductor are simulating a variable inductance or simulating a very large inductance.

This circuit is of limited use in applications relying on the back EMF property of an inductor, as this effect will be limited in a gyrator circuit to the voltage supplies of the op-amp.

Main article: Negative impedance converter |

Creates a resistor having a negative value for any signal generator.

In this case, the ratio between the input voltage and the input current (thus the input resistance) is given by

In general, the components , , and need not be resistors; they can be any component that can be described with an impedance.

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Main article: Precision rectifier |

The voltage drop *V*_{F} across the forward-biased diode in the circuit of a passive rectifier is undesired. In this active version, the problem is solved by connecting the diode in the negative feedback loop. The op-amp compares the output voltage across the load with the input voltage and increases its own output voltage with the value of *V*_{F}. As a result, the voltage drop *V*_{F} is compensated, and the circuit behaves very nearly as an ideal (*super*) diode with *V*_{F} = 0 V.

The circuit has speed limitations at high frequency because of the slow negative feedback and due to the low slew rate of many non-ideal op-amps.

See also: Log amplifier |

The relationship between the input voltage *V*_{in} and the output voltage *V*_{out} is given by

where *I*_{S} is the *saturation current*, and *V*_{T} is the *thermal voltage*.

If the operational amplifier is considered ideal, the inverting input pin is virtually grounded and the op-amp inputs draw no current. So the current flowing from the source through the resistor and diode is

where *I*_{D} is the current through the diode. As known, the relationship between the current and the voltage for a diode is

When the voltage across the diode *V*_{D} is greater than zero, this current can be approximated by

Putting these two formulae together and considering that the output voltage is the negative of the voltage across the diode (*V*_{out} = −*V*_{D}), the relationship is proven.

This implementation does not consider temperature stability and other non-ideal effects.

The relationship between the input voltage and the output voltage is given by

where is the saturation current, and is the thermal voltage.

Considering the operational amplifier ideal, the negative pin is virtually grounded, so the current through the diode is given by

When the voltage is greater than zero, it can be approximated by

The output voltage is given by